Adc having adjustable threshold levels for pam signal processing

ABSTRACT

An ADC system dynamically adjusts threshold levels used to resolve PAM signal amplitudes into digital values. The ADC circuitry includes an analog front end to receive and condition the PAM signal, a low-resolution ADC to digitize the conditioned signal according to a first set of threshold values, and a high-resolution ADC to subsample the conditioned signal to generate subsampled signals. A microprocessor in communication with the low-resolution ADC and the high-resolution ADC derives a statistical value from the subsampled signals, determines an updated set of threshold values, and dynamically replaces the first set of threshold values for the low-resolution ADC with the updated set of threshold values.

RELATED APPLICATIONS

This application is a continuation and claims priority to U.S.application Ser. No. 17/218,017 that was filed on Mar. 30, 2021, whichclaims priority to U.S. Provisional Application 63/002,310 that wasfiled Mar. 30, 2020, both of which are fully incorporated herein byreference. This application is related to U.S. application Ser. No.16/984,096 that was filed on Aug. 3, 2020 and which is also fullyincorporated herein by reference.

BACKGROUND OF THE INVENTION Field of the Invention

The present invention relates generally to digital communicationsystems, and more specifically to an apparatus and method for settingthreshold levels for analog-to-digital conversion of PAM signals.

Description of Related Art

Real world natural signals are analog signals that are continuous intime and amplitude. In modern communication systems, ananalog-to-digital converter (ADC) is used to digitize the analog signalinto a binary representation of discrete amplitudes evenly spaced byuniform a time interval. The time interval by which the analog inputsignal is digitized is called the sampling rate, for example, one sampleevery 40 picoseconds equates to a sampling rate of 25 G samples persecond (25 GS/s). In circuit implementations, an ADC is typicallypreceded by an analog front end (AFE) and sometimes an analog equalizer(EQ) to receive and condition the analog signal before conversion by theADC.

To convert an analog signal having amplitude that varies continuouslyinto a digital representation of discrete amplitudes, the ADCestablishes threshold levels to decide whether a sampled analogamplitude that lies between adjacent discrete digital amplitudes shouldbe given the higher discrete value or the lower discrete value. Anexample is given in FIGS. 1-2. FIG. 1 shows an analog signal 10 havingan amplitude A that varies in the vertical direction over time t. FIG. 2shows a digital representation 20 of signal 10 by a 6-bit ADC thatsamples signal 10 at a sampling rate of one sample per time interval,where the time interval T is equal to the width of a rectangular pulse.Each time the 6-bit ADC samples signal 10, it compares the sampledamplitude to a threshold and, based on that comparison, assigns a 6-bitnumber K between 000000 (zero) and 111111 (63), where 111111 correspondsto the analog input amplitude (e.g. voltage) being greater than athreshold of 1.0, as shown at sample 21. A series of thresholds arethereby set for every 1/63rd fraction of amplitude. For example, if thesampled analog signal lies between 40/63 and 41/63, e.g. at sample 22,the sampled amplitude exceeds the 40/63 threshold but is less than the41/63 threshold, and so the digitized amplitude is assigned a value of40/63, and represented as 101000.

Computer-based data transmission typically uses an NRZ (PAM2) codingscheme or a PAM4 coding scheme. Compared to NRZ, PAM4 offers certainadvantages. For the same baud rate, PAM4 coding has half the Nyquistfrequency and twice the throughput, because, with PAM4 each voltagelevel (or “symbol”) represents two bits of information. Many benefitsarise from halving the Nyquist frequency, including doubling the densityof data, achieving higher resolution using the same oversampling rate,and having the same total noise power spread over a wider frequency sothat the noise power in bandwidth diminishes. But there are also somedisadvantages. The PAM4 signal has ⅓ the amplitude of a similar NRZsignal, and consequently, the PAM4 signal has a less desirablesignal-to-noise ratio (SNR). That is a result of the tighter spacingbetween voltage levels in PAM4 signaling, making a PAM4 signal generallymore susceptible to noise.

FIG. 3 shows an eye diagram 30 that illustrates PAM4 modulation. In PAM4signal processing, the analog signal is modulated to represent any oneof four nominal levels of amplitude. The eye diagram shows multiplesuperimposed waves of a PAM4 signal as each wave transitions among thefour levels. Noise and other signal impairments cause amplitudevariations in the waves that are evident when the signals aresuperimposed. PAM4 modulation sets the nominal levels at relativemagnitudes (e.g. voltages) of −3, −1, +1, +3 as shown on the left-handside of the figure. To represent and distinguish among these fourlevels, a 2-bit ADC is sufficient to convert the analog signal torespective binary values of 00, 01, 10, 11. As shown on the right-handside of FIG. 3, the 2-bit ADC uses three threshold levels −2, 0, +2 todetermine which of the four nominal levels the ADC should assign to awave sampled during the sampling period P. The 2-bit ADC thereforeprovides a resolution of 2.0 for a sampled signal; that is, if thesampled signal input to the ADC is less than −2, the ADC output is 00;if the input is greater than or equal to −2 but less than 0, the ADCoutput is 01; if the input is greater than or equal to 0 but less than+2, the ADC output is 10; and if the input is greater than or equal to+2, the ADC output is 11.

In practical systems, due to the lower SNR in PAM4 modulation and todistortion of the input signal from impairments in optical components,temperature variations, and other phenomena, sampled signal levels canerroneously cross a threshold level, resulting in “cross-threshold”error in the binary output of the ADC. The distortion can be minor orsevere and varies depending on the components used in the signal path.For example, a sampled wave that should communicate an amplitude of +1is distorted by an error of +1.2. Sampling then returns a value of +2.2to the ADC, which misinterprets the signal and assigns a binary value of11. And because the SNR and signal impairment vary over time, errorpropagation in the ADC becomes difficult to predict and remedy.

What is needed is an advancement in ADC circuit design that minimizescross-threshold error in PAM4 signal processing.

SUMMARY OF THE INVENTION

The present invention overcomes the foregoing problems by apparatus andmethods disclosed herein that provide an ADC having adjustable thresholdlevels that improve overall SNR in circuitry receiving an analog datasignal. The invention uses a low-resolution, high-speed ADC to sampleand convert a PAM signal to digital form by resolving signal amplitudesusing a set of threshold levels. A high-resolution, low-speed ADCsubsamples input to the low-resolution, high-speed ADC and stores datafrom which statistical values may be derived representing amplitudevariations that arise from signal impairment. The low-speed, highresolution ADC then dynamically updates the threshold levels used by thelow-resolution, high-speed ADC to improve SNR and reduce the overallerror rate. The invention has particular application in PAM4 signalprocessing.

One embodiment of the invention provides receiving circuitry incommunication with an optical or electrical medium. The receivingcircuitry includes an analog front end (AFE) to convert an analog signalreceived from the optical or electrical medium into an analogconditioned signal, a low-resolution analog-to-digital converter (ADC)to digitize the analog conditioned signal according to a first set ofthreshold values, and a high-resolution ADC to subsample the analogconditioned signal to generate a plurality of subsampled signals. Amicroprocessor in communication with the low-resolution ADC and thehigh-resolution ADC is configured to derive one or more statisticalvalues from the plurality of subsampled signals, determine a set ofupdated threshold values from the one or more statistical values, anddynamically replace the first set of threshold values for thelow-resolution ADC with the updated set of threshold values.

In another embodiment of circuitry according to the invention, thelow-resolution ADC is further configured to digitize the analogconditioned signal according to a first set of nominal values. Themicroprocessor is configured to determine a set of updated nominalvalues as a function of one or more statistical values. The statisticalvalues for the nominal values or the threshold values may be a mean, astandard deviation, a peak-to-peak value, a center value, or anothervalue predictive of signal deviation or impairment. In various otherembodiments of the invention, the low-resolution ADC digitizes theanalog conditioned signal by sampling the analog conditioned signal toobtain a plurality of sampled signal values, comparing the plurality ofsampled signal values with the first set of threshold values, andassigning binary codes to the sampled signal values based on thecomparison. In another embodiment of the invention, circuitry fordynamically adjusting ADC thresholds includes a plurality oflow-resolution ADCs and a plurality of high-resolution ADCs thatrespectively sample and subsample an analog conditioned signal anddigitize it to a series of binary values.

Another embodiment of the invention is disclosed as a system on a chip(SOC) configured to digitize a four-level pulse amplitude modulated(PAM) signal. The SOC includes a low-resolution ADC to receive anddigitize an analog conditioned signal according to a first set ofthreshold values, a high-resolution ADC to subsample the analogconditioned signal to generate a plurality of subsampled signals, and amicroprocessor in communication with the low-resolution ADC and thehigh-resolution ADC. The microprocessor is configured to derive one ormore statistical values from the plurality of subsampled signals,determine a set of updated threshold values from the one or morestatistical values, and dynamically replace the first set of thresholdvalues for the low-resolution ADC with the updated set of thresholdvalues.

Another embodiment of the invention is disclosed as a method to improvesignal-to-noise ratio (SNR) in a communication system susceptible tosignal impairment by an optical or electrical medium. The methodincludes the following salient steps: receiving an incoming signal andconditioning the incoming signal to form a conditioned signal, samplingthe conditioned signal according to a first set of threshold values,subsampling the conditioned signal to obtain a plurality of subsampledsignals, deriving one or more statistical values from the plurality ofsubsampled signals, determining a set of updated threshold values fromthe one or more statistical values, and replacing the first set ofthreshold values with the updated set of threshold values and sampling asubsequent conditioned signal according to the updated set of thresholdvalues.

BRIEF DESCRIPTION OF THE DRAWINGS

Other systems, methods, features and advantages of the invention will beor will become apparent to one with skill in the art upon examination ofthe following figures and detailed description. It is intended that allsuch additional systems, methods, features and advantages be includedwithin this description, be within the scope of the invention, and beprotected by the accompanying claims. Component parts shown in thedrawings are not necessarily to scale, and may be exaggerated to betterillustrate the important features of the invention. Dimensions shown areexemplary only. In the drawings, like reference numerals may designatelike parts throughout the different views, wherein:

FIG. 1 is a graph of an analog carrier signal having an amplitude thatvaries over time.

FIG. 2 is a graph of digital output of a 6-bit ADC that has sampled theanalog signal of FIG. 1.

FIG. 3 is an eye diagram illustrating nominal signal levels in aconventional PAM4 scheme, along with threshold levels foranalog-to-digital conversion of the data signal.

FIG. 4 is block diagram of one embodiment according to the invention ofa logic circuit comprising a 3-bit flash ADC for adjusting thresholdlevels for PAM signal processing.

FIG. 5 is a block diagram of one embodiment of a circuit implementationof the present invention for PAM4 signal processing using an interleavedFFE, DFE, and M-bit ADC.

FIG. 6 is a block diagram illustrating usage of a low-speed, highresolution ADC for higher-accuracy subsampling of equalized signals forcomputing PAM4 threshold statistics.

FIG. 7 is an eye diagram illustrating adjustable thresholds achievedusing an ADC according to the invention in a PAM4 signal processingscheme.

FIG. 8 is a scatter chart of samples taken from a PAM4 signal by alow-speed, high resolution ADC configured according to an embodiment ofthe present invention.

FIG. 9 is a histogram of samples taken from a PAM4 signal by alow-speed, high resolution ADC configured according to an embodiment ofthe present invention.

FIG. 10 is a bar graph showing a statistical distribution of CMP slicebins.

FIG. 11 is a bar graph showing a statistical distribution of PAM4 slicebins.

FIG. 12 is a process flow diagram illustrating salient steps in oneembodiment of a method according to the invention for reducing SNR in anoptical or electrical medium.

DETAILED DESCRIPTION OF THE INVENTION

The following disclosure presents apparatus and methods of the presentinvention for an ADC having adjustable threshold levels that improveoverall SNR in circuitry receiving an analog data signal over optical,electrical, or other media. The invention uses a low-resolution,high-speed ADC to sample and convert a PAM signal to digital form byresolving signal amplitudes using a set of threshold levels. Ahigh-resolution, low-speed ADC subsamples input to the low-resolution,high-speed ADC and stores data from which statistical values may bederived that represent amplitude variations that arise from signalimpairment. The low-speed, high resolution ADC then dynamically updatesthe threshold levels used by the low-resolution, high-speed ADC toimprove SNR and reduce the overall error rate. The invention hasparticular application in PAM4 signal processing.

An ADC having adjustable threshold levels for PAM4 signal processing inaccordance with the principles of the present invention may use a hybridsignal processing scheme as set forth more fully in co-pending U.S.application Ser. No. 16/984,096, which is incorporated by referenceherein and which is owned by the assignee of the present invention. Asdescribed in the co-pending application, the hybrid signal processingscheme receives a high-speed data signal (e.g. 25 GHz or higher) at anAFE. Prior to digitizing the high-speed signal, the signal isconditioned using an interleaving and summing technique whereby sampledsignal values from interleaved analog feed-forward equalizers (FFEs) aresummed with output from interleaved decision feedback equalizers (DFEs).The summed values are then converted by an ADC to generate a digitalversion of the data signal.

Due, however, to the low SNR and signal impairment inherent in PAM4, anADC having a bit size greater than 2 may be employed in the presentinvention to capture information representing the non-uniformity (orerror) present in each sample. An illustrative implementation isdescribed herein that uses a 3-bit ADC for this purpose, though theinvention is not limited to this particular bit size of ADC. The 3-bitADC improves the resolution to 1.0 relative to a full-scale range of−3.0 to +3.0. The extra bit of information provided by the 3-bit ADCenables statistical analyses of samples, which, in turn, enables methodsfor dynamically adjusting ADC thresholds to improve performance.

FIG. 4 shows a block diagram of one embodiment according to theinvention of a logic circuit 40. Logic circuit 40 may be a 3-bit flashADC. Circuit 40 converts an analog signal into digital form by encodingboth signal level and error in binary form. The coding technique is oneexample illustrating a method that enables further statistical analysisof digitized samples, for use in adjusting threshold levels for PAMsignal processing. At the left-hand side of the figure, an analog signal41 is received as input to be sampled by circuit 40. In one embodimentof the invention, the signal 41 may an analog signal received by an AFEand further conditioned by an EQ stage of the overall circuitimplementation shown in FIG. 5. With reference again to FIG. 4, signal41 is fed in parallel to a comparator stage consisting of multiplecomparators (CMPs), which in this example are seven CMPs 51, 52, 53, 54,55, 56 and 57. Each CMP has two inputs and one output. The two inputs ateach CMP consist of a threshold value and a signal input. Each signalinput receives signal 41, as shown. The threshold value for each CMP isone of multiple different setpoints that span the desired range ofamplitudes expected for the particular PAM scheme. For example, in thepresent PAM4 implementation, the amplitudes of the samples in signal 41are expected to range from −3 to +3 (e.g. VDC) in evenly spacedincrements of 1 unit. Thus, the sequence of threshold values for CMPs51, 52, 53, 54, 55, 56 and 57 consists respectively of −3, −2, −1, 0,+1, +2 and +3, as shown. Each CMP functions by comparing signal 41 toits threshold. If signal 41 is equal to or less than the threshold, theoutput of the CMP is set to 0. If signal 41 is greater than thethreshold, the output of the CMP is set to 1.

The next stage in circuit 40 is a multiplexor (MUX) stage, whichprocesses outputs from the CMPs. Each MUX 61, 63, 65, 67 has two signalinputs—labeled 0 and 1—and one control input: 62, 64, 66 or 68, asshown. Each MUX 61, 63, 65, 67 produces one output 69, 70, 71 or 72,respectively. Each MUX signal input receives the output from one of theCMPs or the output from another MUX. Each MUX control input alsoreceives the output from one of the CMPs. If the control input to a MUXis 0, the MUX passes to its output the signal at its 0-labeled input. Ifthe control input to a MUX is 1, the MUX passes to its output the signalat its 1-labeled input.

The final stage in circuit 40 is an output stage that generates a 3-bitbinary representation of each sample received as signal 41. Each of thethree bits may be generated using a bistable logic device configured toprocess the outputs from one or more of the MUX devices and/or one ormore of the CMP devices. In the present example, the bistable logicdevices at the output stage are D flip-flops (DFFs) that are modeled ashaving a single input and a single output. Three DFFs 73, 74 and 75 areused in circuit 40 to respectively generate outputs 76, 77, 78, whereoutput bit 76 represents the PAM4 least significant bit (LSB), outputbit 77 represents the PAM4 most significant bit (MSB), and output 78represents the error. Each DFF will store and output whatever logiclevel is applied to its input. Thus, in this example, each DFF can holda logical output value of either 0 or 1. Together, the three DFFscomprise the 3-bit representation of a data signal that achieves thedesired higher resolution in an ADC of the present invention.

In circuit 40, each CMP, MUX, and DFF may be configured using knowncircuit design and fabrication techniques. The number and configurationof the CMPs, MUX, and DFF devices used in an ADC according to theinvention may vary depending on PAM scheme, threshold levels, desiredresolution, microchip limitations or other design considerations.Sampling may be effected using a plurality of track-and-hold andsample-and-hold circuitry, to respectively sample and resample theanalog conditioned signal. To better illustrate how these devicescooperate in the configuration of circuit 40 to achieve the desired3-bit output, several numerical examples are provided in the followingparagraphs.

Example 1: input signal 41=+2.9. An input signal level of +2.9 receivedby circuit 40 at the CMP stage will cause the following CMP outputs: CMP51 to CMP 56=1, and CMP 57=0. As a result, at MUX 61 control signal 62=1therefore MUX 61 passes the output of CMP 53 through so that MUX output69=1. At MUX 63, control signal 64=1 therefore MUX 63 passes the outputof CMP 57 through so that MUX output 70=0. At MUX 65, control signal66=1 therefore MUX 65 passes the output of CMP 56 through so that MUXoutput 71=1. At MUX 67, control signal 68=1 therefore MUX 67 passesoutput 70 through so that MUX output 72=0. At the output stage, DFF 73passes through signal 71 therefore output 76=1. DFF 74 passes the outputof CMP 54 directly therefore DFF output 77=1. And DFF 75 passes throughsignal 72 therefore DFF output 78=0. The final 3-bit output of circuit40 is therefore 011. The first two digits, 11, indicate the highest ofthe four signal values in PAM4, which in this example is +3, which isthe ADC representation of the sampled input signal. The leading bit isthe error bit, where an error bit of 1 it indicates a positive error,and an error bit of 0 indicates a negative error. In this example, theleading 0 indicates negative error or an input less than +3. Thus, for asampled value of +2.9 the ADC yields 011, which is +3 with negativeerror.

Example 2: input signal=+1.1. An input signal level of +1.1 received bycircuit 40 at the CMP stage will cause the following CMP outputs: CMP 51to CMP 55=1, and CMP 56 to CMP 57=0. At MUX 61 control signal 62=1therefore MUX output 69=1. At MUX 63 control signal 64=0 therefore MUX63 passes the output of CMP 55 through so that MUX output 70=1. At MUX65, control signal 66=1 therefore MUX 65 passes the output of CMP 56through so that MUX output 71=0. At MUX 67, control signal 68=1therefore MUX 67 passes output 70 through so that MUX output 72=1. Atthe output stage, DFF 73 passes through signal 71 therefore output 76=0.DFF 74 output 77=1, and DFF 75 passes through signal 72 therefore DFFoutput 78=1. The final 3-bit output of circuit 40 is therefore 110. Thefirst two bits, 10, represent the 3rd highest value of the PAM4 signals,or +1. The error bit 1 indicates a positive error. Thus, for a sampledvalue of +1.1 the ADC yields 110, which is +1 with positive error.

Example 3: input signal=−1.1. An input signal level of −1.1 received bycircuit 40 at the CMP stage will cause the following CMP outputs: CMP 51to CMP 52=1, and CMP 53 to CMP 57=0. At MUX 61 control signal 62=1therefore MUX 61 passes through the output of CMP 53 so that MUX output69=0. At MUX 63 control signal 64=0 therefore MUX 63 passes the outputof CMP 55 through so that MUX output 70=0. At MUX 65, control signal66=0 therefore MUX 65 passes the output of CMP 52 through so that MUXoutput 71=1. At MUX 67, control signal 68=0 therefore MUX 67 passesoutput 69 through so that MUX output 72=0. At the output stage, DFF 73passes through signal 71 therefore output 76=1. DFF 74 output 77=0, andDFF 75 passes through signal 72 therefore DFF output 78=0. The final3-bit output of circuit 40 is therefore 001. The first two bits, 01,represent the 2nd highest value of the PAM4 signals, or −1. The errorbit 0 indicates a negative error. Thus for an input of −1.1. the ADCyields 001, which is −1 with negative error.

FIG. 5 shows a block diagram of an overall circuit implementation 80 forPAM4 signal processing according an embodiment of the invention. Circuit80 includes an interleaved analog equalizer stage (EQ) that includes FFE81, an interleaved analog DFE 82, and a summing stage 83. In variousembodiments, one or more of components 81, 82 and 83 make up or formpart of an AFE portion of receiver circuitry, which may include signalconditioning circuitry, sampling circuitry, and amplifier circuitry foramplifying or attenuating the analog signal. Operation of theinterleaved FFE and DFE is described in greater detail in co-pendingU.S. application Ser. No. 16/984,096. Generally, to facilitate circuitimplementation in high-speed data processing applications, an analogdata signal received at an AFE of the present invention preferablyemploys a hybrid interleaved sampling technique whereby the signalinterleaved by the FFE 81 comprising FFE₀, FFE₁ . . . FFE_(N) iscombined at summing stage 83 with interleaved output from DFE 82comprising DFE₀, DFE₁ . . . DFE_(N). At 86, each output EQ_(N) ofsumming stage 83 has the form EQ_(N)=FFE_(N)+DFE_(N), where FFE_(N) isthe output of FFE 81 for the Nth sample, DFE_(N) is the output of DFE 82for the Nth sample, and where N is an integer. EQ outputs EQ₀, EQ₁, . .. EQ_(N) are then fed to an interleaved M-bit ADC 84, which has one bitfor each interleaved analog EQ output. ADC 84 may be a high-speed, lowresolution ADC configured with adjustable threshold levels forgenerating a digital version 85 of the data signal. M can be any numberof bits, for example, 3 bits as in embodiments described above. The ADCoutput data 85 can then be further processed in the digital domain usingdigital signal processing to generate the PAM data and other usefulinformation.

FIG. 6 shows a block diagram of an overall system 60 according to theinvention for an ADC having adjustable threshold levels. System 60 usesa low-speed, high resolution ADC 88 in conjunction with the high-speed,low resolution ADC 84 shown in circuit implementation 80. ADC 88 and itsassociated circuitry may be utilized to achieve higher-accuracysubsampling of equalized signals for computing PAM4 threshold statisticsaccording to the invention. ADC data bits 85 are generated by thehigh-speed, low resolution ADC 84 of circuit 80. In the 3-bit exampledescribed herein, data bits 85 may consist of ADC₀ through ADC₇. Thelow-speed, high resolution ADC 88 may be connected to one or more of thesumming nodes of the eight interleaved channels, such as summing node 83in this example. ADC 88 may operate according to the same generalprinciples described for circuit 40, but may be customized for higherresolution by generating a greater number of bits (e.g. >3) forrepresenting a sampled signal amplitude and associated error.Accordingly, ADC 88 may be configured to subsample the equalized signal86 by using a greater number of bits per sample than used by ADC 84 toachieve a much higher resolution for error detection among the samples.ADC 88 may advantageously operate at a lower processing speed, as itspurpose is not to digitize signal 41 at the data signal transmissionfrequency, but rather to subsample the output 86 to compile statisticsrelevant to detecting variation in nominal PAM signal leveldisplacements that occur in aggregate. In one embodiment, ADC 84 samplesthe analog conditioned signal, output 86, at a rate between about 100MS/s and 100 GS/s. In the same or another embodiment, ADC 88 subsamplesthe output 86 at a rate between about 100 (MS/s)/n and 100 (GS/s)/mwhere m is an integer greater than 1.

In other embodiments of the invention, as indicated by the stackedconfiguration of system blocks in FIG. 6, circuitry for dynamicallyadjusting ADC thresholds may include a plurality of low-resolution ADCsand a plurality of high-resolution ADCs. Each pair of low and highresolution ADCs respectively sample and subsample an analog conditionedsignal and digitize it to a series of binary values. Each pair in theplurality of pairs may operate on a separate data signal, or ondifferent phases of the same data signal.

Various statistics and histograms may derived from the collection ofsignals subsampled by ADC 88. The ADC 88 is configured to store thesubsampled signals in memory 91, generally at a capacity of k samples,each k sample having n bits resolution, where k and n are integers. Thepurpose of collecting these statistics is to recognize when and whethersignal impairment has caused a predictable variation in the amplitude ofthe data signal with respect to each nominal PAM level. In one example,a statistic of interest may be the arithmetic mean of ADC outputsassigned to the highest nominal PAM level. In a PAM4 scheme, where aninput level that exceeds a threshold of +2 is interpreted as +3, asetpoint module 92 by means of a microprocessor reads subsampled signals89 stored in memory 91 by ADC 88. Then, using an executable programstored in the memory 91, the microprocessor of setpoint module 92calculates a statistic of interest, such as the mean value for all ADCinput levels that resulted in an output of +3 over predetermined timeperiod. If the calculated mean value is +3+/−delta, the setpoint module92 may dynamically adjust the setpoint level in the high speed, lowresolution ADC to +2+/−delta and thereby improve the accuracy of the ADCsystem. According to the invention, setpoint module 92 may functioneither as an on-chip microprocessor or off-chip microprocessor. In oneembodiment, as an on-chip microprocessor, setpoint module 92 forms anintegral part of the circuitry of ADC 88.

As the data signal is being received and conditioned at the AFE, the lowspeed, high resolution ADC 88 runs in the background, monitoring inputsignal levels fed to the high speed, low resolution ADC 84 and storingvalues in memory 91 readable by the setpoint module 92 for statisticalcalculations for determining updated threshold values. Algorithms fordetermining an updated threshold values may run at system startup,periodically, or conditionally. In one implementation, when thestatistics calculated by the setpoint module 92 indicate that anexisting threshold level (e.g. −2, 0, +2) is sufficiently offset from anupdated threshold level, the setpoint module sends a command 93containing the updated threshold level to ADC 84. The existing thresholdlevel in ADC 84 is then dynamically adjusted so that the existingthreshold level is updated to match the updated threshold levelaccording to the instructions of command 93. The updated threshold levelthereby becomes a new existing threshold level. Dynamic adjustment of athreshold level means that the adjustment occurs while the analog signalis being received and conditioned by the AFE stage of the circuitry. Inthe same manner, the setpoint module 92 may update an existing nominallevel (e.g. −3, −1, +1, +3). For example, the statistical analysis maycalculate both a mean and a standard deviation for amplitudes thatrepresent a particular nominal value. Command 93 may instruct ADC 84 toadjust the nominal value to match the mean, and to adjust one or morethreshold values to a setpoint that matches the mean plus a multiple ofthe standard deviation.

FIG. 7 shows an eye diagram 90 illustrating adjustable thresholdsachieved using an ADC according to the invention in a PAM4 signalprocessing scheme. Like diagram 30, diagram 90 shows multiplesuperimposed waves of a PAM4 signal as each wave transitions among foursignal levels. Diagram 90 differs from diagram 30, however, because eachof the existing nominal levels −3, −1, +1, +3 in diagram 30 has beenadjusted in diagram 90 to the updated nominal levels −3+Δm3, −1+Δm1,+1+Δp1, +3+Δp3, and in addition, each of the existing threshold levels−2, 0, +2 in diagram 30 has been adjusted in diagram 90 to the updatedthreshold levels −2+Δm2, 0+Δ0, +2+Δp2. The adjustments have been made bythreshold setpoint module 92 after running statistical analyses of datacollected by ADC 88 that determined the updated nominal and updatedthreshold levels. Each adjustment is a “delta” value represented by thesymbol A, and each delta value may be positive or negative. Thenotations m3, m1, p1, p3, m2, 0, and p2 indicate the nominal orthreshold value to which each delta value applies.

Eye diagram 90 gives a visual indication that the updated thresholdlevels lie approximately at a geometric center of each of the eye-shapedspaces within sampling period P. In one embodiment, a statisticalanalysis run by setpoint module 92 computes a statistical valuerepresenting such geometric center.

According to the invention, setpoint module 92 periodically orconditionally runs statistical analyses and accordingly adjusts nominaland threshold setpoint levels to compensate for impairments in the datasignal that vary over time. Adjusting the levels in this manner improvesSNR, decreases the overall bit error rate, and generally improves ADCperformance. FIGS. 8 to 11 are various charts and graphs that can bederived from data collected by the low speed, high resolution ADC 88 andstored in memory 91. The graphs provide a visual indication of thevariance of signal levels processed by the ADC.

FIG. 8 shows a scatter chart 100 of samples taken from a PAM4 signal bya low-speed, high resolution ADC configured according to an embodimentof the present invention. The samples may be taken over any time periodof interest and may be used to calculate statistics attributable to thesamples that may be predictive of signal deviation or impairment, suchas, but not limited to, mean, standard deviation, variance, peak-to-peakvalue, center value, median, maxima and minima. Signal amplitudes areplotted along the vertical axis, and time along the horizontal. Thisscatter chart shows horizontal clusters of samples, each having valuesthat vary above and below one of four nominal PAM4 levels. In oneimplementation, a center value statistic generated by the setpointmodule 92 may represent a midpoint between peak-to-peak distributions ofany of the four clusters shown in the scatter chart. FIG. 9 shows ahistogram 110 derived from a similar set of samples. Here signalamplitudes are shown along the horizontal axis, with the total count ofinstances plotted along the vertical. In one implementation, a medianvalue statistic generated by the setpoint module 92 may represent a peakvalue of any one of the four distributions shown in the histogram. FIG.10 shows a bar graph 120 to illustrate a similar distribution of samplesamong CMP slicer bins, with signal amplitude on the horizontal and totalcount on the vertical. FIG. 11 shows a bar graph 130 to illustrateanother statistical distribution of samples mapped into PAM4 bins, witheach of four bins along the horizontal representing a nominal signallevel and the count measured along the vertical, over a time period ofinterest.

FIG. 12 shows a process flow diagram illustrating salient steps in oneembodiment of a method 140 according to the invention for improving SNRin an optical or electrical medium. The process steps are to beinterpreted in light of the disclosure herein. Method 140 begins at step141, at which an incoming analog signal is received and conditioned toform a conditioned signal. At the next step 142, the conditioned signalis sampled according to a first set of threshold values. Next, at step143, the conditioned signal is subsampled to obtain a plurality ofsubsampled signals. Next, at step 144, one or more statistical valuesare derived from the plurality of subsampled signals. Then at step 145 aset of updated threshold values is determined from the one or morestatistical values. At the final step 146 the first set of thresholdvalues is dynamically replaced with the updated set of threshold valuesand a subsequent conditioned signal is sampled according to the updatedset of threshold values.

Exemplary embodiments of the invention have been disclosed in anillustrative style. Accordingly, the terminology employed throughoutshould be read in a non-limiting manner. Although minor modifications tothe teachings herein will occur to those well versed in the art, itshall be understood that what is intended to be circumscribed within thescope of the patent warranted hereon are all such embodiments thatreasonably fall within the scope of the advancement to the art herebycontributed, and that that scope shall not be restricted, except inlight of the appended claims and their equivalents.

1-20. (canceled)
 21. A method to improve signal to noise ratio due tosignal impairment by an optical or electrical medium, the methodcomprising: receiving an incoming signal from the optical or theelectrical medium and conditioning the incoming signal to form an analogconditioned signal; sampling the analog conditioned signal according toa first set of threshold values; subsampling the analog conditionedsignal to obtain a plurality of subsampled signals; deriving one or morestatistical values from the plurality of subsampled signals; determininga set of updated threshold values from the one or more statisticalvalues; and dynamically replacing the first set of threshold values withthe updated set of threshold values.
 22. The method of claim 21 furthercomprising sampling a subsequent conditioned signal according to theupdated set of threshold values.
 23. The method of claim 21, wherein thesampling step comprises digitizing the analog conditioned signalaccording to a first set of nominal values, and wherein the determiningstep determines a set of updated nominal values as a function of the oneor more statistical values.
 24. The method of claim 21, wherein thesampling step further comprises digitizing the analog conditioned signalby (1) sampling the analog conditioned signal to obtain a plurality ofsampled signal values, (2) comparing the plurality of sampled signalvalues with the first set of threshold values, and (3) assigning binarycodes to the sampled signal values based on the comparison.
 25. Themethod of claim 21, wherein the receiving step is performed by analogfront end (AFE) circuitry that includes one or both of a feed-forwardequalizer (FFE) and a decision feedback equalizer (DFE).
 26. The methodof claim 21, wherein the statistical values comprise one or more of amean value, a standard deviation, a peak to peak value, and a centervalue.
 27. The method of claim 26, wherein the center valuesubstantially defines a midpoint between peak-to-peak distributions ofthe plurality of subsampled signals.
 28. The method of claim 26, whereinthe center value substantially defines a geometric center of an eyediagram derived from superimposed waves of the analog conditionedsignal.
 29. The method of claim 21, wherein the set of updated thresholdvalues is determined by a microprocessor executing a program stored inmemory.
 30. The method of claim 29, wherein the set of updated thresholdvalues are determined on chip or off chip.
 31. The method of claim 21,wherein the receiving step is performed by analog front end (AFE)circuitry that includes signal conditioning circuitry, samplingcircuitry, and amplifier circuitry.
 32. The method of claim 31, whereinthe sampling circuitry comprises a track-and-hold circuitry.
 33. Themethod of claim 31, wherein the amplifier circuitry attenuates oramplifies the analog signal.
 34. The method of claim 21, wherein thesampling step further comprises digitizing the analog conditioned signalto a binary value.
 35. The method of claim 21, wherein at least oneupdated threshold value in the set of updated threshold values isdetermined as a function of successive signals subsampled from theanalog conditioned signal.
 36. The method of claim 35, wherein the atleast one updated threshold value is determined at one or more of startup, periodically, or conditionally.
 37. The method of claim 21, whereinthe sampling step comprises sampling the analog conditioned signal at arate between about 100 MS/s and 100 GS/s and wherein the subsamplingstep comprises subsampling the analog conditioned signal at a ratebetween about 100 (MS/s)/m and 100 (GS/s)/m, wherein m is an integergreater than
 1. 38. The method of claim 21, further comprising storingthe subsampled conditioned signals at a capacity of k samples, each ksample having n bits resolution, where k and n are integers.